Current equalizing circuit

ABSTRACT

A circuit supplies a current (I) in which the current variations (I L ) having been equalized according to a given relationship. In order to obtain an equalization characteristic having at least two slopes, the circuit uses the switching of the current sources (xI o , yI o  and zI o ) by means of switching stages (T 1 , T 2 , T 14 ). The output current I passing through the current output stages T 3  and T 4  thus fluctuates between two levels according to the desired equalizing relationship.

BACKGROUND OF THE INVENTION

The present invention has for its object to provide an equalizing circuit intended for producing an output current which has a given current characteristic as a function of the value of an input current the current characteristic having a maximum and a minimum value, which circuit comprises a means for producing a first current which is proportional to the input current, connected in series with a first current source producing a second current which is proportional to a reference current, in order to produce a first resulting current which is positive when the first current is higher than the second current and zero in the opposite case, a first switching stage arranged for being non-conductive when the first resulting current is zero, and passed through thereby when it is positive a second switching stage arranged for being passed through by the same current as the first switching stage, a second current source arranged for supplying a third current which is proportional to the reference current and connected in series with the second switching stage, in a manner such as to generate a second resulting current which is positive when the third current is higher than the resulting first current, a third switching stage arranged for not conducting when the second resulting current is zero, and passed through thereby when it is positive a first current output stage arranged for supplying a current which is equal to the current passing through the third switching stage and a second current output stage connected in parallel with the first current output stage arranged for supplying a current which is equal to the reference current, whose value is thus the said minimum value of the output current characteristic.

Such a circuit has been used for effecting a gain control of a telephone receiver, which circuit is commercially available referenced as TEA 1061.

A circuit having the same object but having a different structure has also been described in the U.S. Pat. No. 3,810,032.

The two circuits enable obtaining a current which linearly depends on an input current, between a bottom and a top limit. Such circuits are used specifically in subscriber telephone sets which are fed with a given voltage, generally 48 volts, from an exchange, the current which the subscriber terminal disposes of being smaller the more remote from the exchange the terminal is situated. In order to make the sensitivity of the telephone set independent of the length of the subscriber line and thus homogenize the listening level among the subscribers the subscriber set comprises an amplifier stage whose gain ratio depends on the current supplied and the above supply current is provided by an equalizing circuit fed by the line current, the equalization being effected according to a linear relationship as near to the theoretical curve as possible.

However, if the lines are very long and/or when moderate lengths of line sections are used, the theoretical curve stretches out over a larger dynamic range and tends to become more curved.

The above linear equalization is thus no longer sufficiently precise, which is unfavorable for certain subscriber stations.

SUMMARY OF THE INVENTION

It is an object of the invention to eliminate this disadvantage by proposing a circuit which basically provides an equalization having at least two linear regions with different slopes, in order to approach such curves more particularly but not exclusively with sufficient precision, or to approach the more conventional curves with greater precision.

The arrangement according to the invention is characterized in that it comprises at least an equalizing circuit connected in parallel with one of the first and second switching circuits and comprising on the one hand a third current source arranged for supplying a fourth current which is proportional to the reference current, connected in series with a fourth current source arranged for supplying a current in proportion to the current supplied by a first switching stage and on the other a blocking circuit arranged for connecting the fourth current source in parallel with at least one of the first and second switching circuits when the current passing through the fourth current source is larger than the fourth current.

According to an embodiment of the invention, the first switching circuit comprises a first transistor whose collector-emitter path is connected in parallel with the first current source and a second transistor whose base-emitter path is connected in parallel with the collector-emitter path of the first transistor, and the second switching stage comprises a third transistor whose base is connected to that of the first transistor. The third switching circuit may comprise a fourth transistor whose collector-emitter path is connected in parallel with the second switching stage and a fifth transistor whose base-emitter path is connected in parallel with the collector-emitter path of the fourth transistor and the first output stage may comprise a sixth transistor whose base is connected to that of the fourth transistor.

Thus the desired result is achieved with a circuit which remains simple and the parameters of the circuit (slopes, slope changes) can be adjusted without any difficulty.

According to an advantageous embodiment at least one blocking circuit comprises a first diode connected in series with the said means for supplying the first current which is proportional to the input current, and second and third diodes connected in parallel with the fourth current source. An equalization curve is thus obtained having two slopes corresponding, more specifically, with the curves drawn for the subscriber stations.

According to an embodiment, at least one blocking circuit comprises a fourth diode connected in series with the second current source and fifth and sixth diodes connected in parallel with the fourth current source.

According to a preferred embodiment, corresponding with an equalization having three slopes corresponding, more specifically, with the case of the subscriber stations, two equalizing circuits are connected in parallel with the first switching circuit.

BRIEF DESCRIPTION OF THE DRAWING

The invention will be better understood when reading the following description given by way of non-limiting example, together with the drawing Figures, in which:

FIG. 1 shows a prior-art gain control circuit,

FIG. 2 shows a circuit for producing a current at a given ratio to the line current,

FIG. 3 shows a gain control circuit according to a first embodiment of the invention,

FIG. 4 shows the curves representing the gain characteristic plotted against the line current for a circuit arrangement shown in FIG. 3 and

FIG. 5 shows the curve comprising two sloping lines of the circuit as shown in FIG. 3 adapted to the profile of a given equalization curve,

FIG. 6 shows a gain control circuit according to a second embodiment of the invention,

FIG. 7 shows a curve representing the gain characteristic plotted against the line current for a circuit as shown in FIG. 6 and

FIG. 8 shows the curve comprising two sloping lines of the circuit of FIG. 6 adapted to a given equalization curve,

FIG. 9 shows a gain control circuit according to a preferred embodiment of the invention,

FIG. 10 shows a curve representing the gain characteristic for a circuit as shown in FIG. 9 and

FIG. 11 shows the curve comprising three sloping lines of the circuit of FIG. 9 adapted to the profile of a given equalization curve,

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

A gain control circuit as shown in FIG. 1 (prior art) has for its object to supply a gain control current 1 whose value is I_(o) (minimum gain) when the line current attains a maximum value I_(o) +yI_(o) when the line current has a minimum nominal value, and which linearly varies between these two values when the line current ranges between these two nominal values. With y=1 a correction dynamic of 6 dB will be obtained and 9 dB with y=1.75.

The circuit of FIG. 1 comprises an npn transistor T₀ having at least one emitter which is connected to the common mode pole (ground), a base to which is applied a reference voltage V_(ref) so that its collector-emitter path is passed through by a current xI_(o) (x being the number of emitters of the transistor T₀ or rather the ratio between the surfaces of the emitters of the transistors T₄ (cf below) and T₀), and a collector which is connected to a current source having a strength of k_(o) I_(L). The line current received from a subscriber station and whose value depends on the remoteness of the subscriber relative to the exchange is represented by I_(L), and k_(o) represents a given ratio.

An npn transistor T₁₀ has its emitter connected to ground, its collector connected to that of T₀ and its base connected to that of an npn transistor T₁. The npn transistor T'₁₀ has its base connected to the collectors of the transistors T₀ and T₁₀, its emitter to the bases of the transistors T₁₀ and T₁, and its collector connected to supply a voltage source V. The transistor T₁ has its emitter connected to ground, its collector connected to that of an npn transistor T₂ and also to a current source having a strength of yI_(o), constituted in this case by a pnp transistor T₁₁ which has an emitter connected to the voltage source V, the base connected to the reference potential Vref, and at least one collector connected to those of the transistors T₁ and T₂. An npn transistor T'₂ has its base connected to the collectors of the transistors T₁ and T₂, its emitter to the base of the transistor T₂ and its collector to the voltage source V. An npn transistor T₃ has its base connected to that of the transistor T₂, its emitter to ground, and its collector to that of a transistor T₄ whose emitter is connected to ground and to whose base is applied the voltage Vref so to constitute as a current source I_(o). The common collector of the transistors T₃ and T₄ constitutes the output S of the circuit which forms a current source having the value I. It will be evident that the transistors T₁₀ and T'₁₀ are equivalent to a forward direction diode in the base of T₁, which induces a base-emitter voltage equal to V_(o) in this transistor as long as current is available.

The circuit has three operating zones.

(a) Low I_(L) : k_(o) I_(L) <xI_(o)

The transistor T₀ is saturated and the transistor T₁ is blocked, and thus T₂ is conductive and is passed through by the current yI_(o), as is the transistor T₃ with which it forms a current source. Thus, we have I=I_(o) (1+y) which corresponds with a maximum gain.

(b) Intermediate I_(L) : k_(o) I_(L) >xI_(o)

The transistor T₀ is conductive in the normal fashion. The transistor T₁ is thus conductive (k_(o) I_(L) ·xI_(o)) and the transistor T₂ thus conducts the current yI_(o) -(k_(o) I_(L) -xI_(o)), the same holds for transistor T₃.

Thus we have I=I_(o) (1+y)-(k_(o) I_(L) -xI_(o)).

(c) High I_(L) : k_(o) I_(L) ≧(x+y)I_(o)

The current in T₂ is canceled causing the transistor T₃ to block.

Thus we have I=I_(o) (minimum gain).

FIG. 2 shows a standard schematic of an arrangement diagram with which it is possible to generate a current k_(o) I_(L) and a supply voltage V from a subscriber station. The exchange supplies the subscriber lines with a voltage V_(s) of 48 V. The current I_(L) which the subscriber receives depends on the length of the line between the subscriber and the exchange (line resistance R_(L)), and on the value of the resistance of the exchange (generally 600 Ω). A Zener diode Z is arranged at the input of the subscriber station so as to protect this station against overvoltages, and a capacitor C_(o) of a high value (approximately 100 μf) is inserted between a terminal of an adapting resistor R_(a) and ground. This terminal of the resistor R_(a) provides the supply voltage V.

A resistor R₂ is inserted between the input of the subscriber station and the non-inverting input of an operational amplifier A. Between this input of the amplifier A and ground a capacitor C₂ is inserted having a high value (several μf) intended to filter out the a.c. residual component. The output of the amplifier A is connected to the base of a transistor T₂₀ whose collector is connected to the input of the subscriber station, and whose emitter forms a junction B with on one side a resistor R₁ connected to the junction B and the non-inverting input of the amplifier A, and on the other a resistor R inserted between the junction B and ground and finally connected to the cathode of one of the two diodes D₁ and D₂ connected in series between the inverting input of the amplifier A and junction B.

Assuming that V₁ is the voltage at junction B and V₂ the voltage at the non-inverting input of the amplifier A, and V_(D) the voltage across a diode, we have:

    V.sub.2 -V.sub.1 =2V.sub.D

V₁ =RI_(L)

V₂ =RI_(L) +2 V_(D)

The non-inverting input of the amplifier A is connected to the base of an npn transistor T₃₃ whose emitter is connected to ground across a forward direction diode D₃ and a resistor R' respectively. The collector of the transistor T₃₃ is connected to the base of a transistor T₃₂ whose collector is connected to ground. A transistor T₃₀ has n₁ collectors connected to the base of the transistor T₃₂. The transistor T₂₂ is used because V₂ is connected to ground.

The emitter of the transistor T₃₀ is connected to the voltage V through a resistor R₃₀ and its base is connected to the emitter of transistor T₃₂ and to the base of a transistor T₃₁ whose emitter is connected to the voltage source V through a resistor R₃₁ and which has n₂ collectors (with n₂ ≧1) which supply the current k_(o) I_(L). The resistor R' terminal not connected to ground has a potential of V₃.

We have:

    V.sub.3 =V.sub.2 -2V.sub.D ≃V.sub.1 =RI.sub.L

The current I' which passes through the resistor R' has a value of: ##EQU1## The transistors T₃₀ and T₃₁ form a current source at a ratio of n₂ /n₁ (or more generally, at the ratio of the surfaces of their collectors).

We have: ##EQU2##

FIG. 2 also shows an arrangement for obtaining the voltage Vref for the pnp transistor current sources (and a voltage V'ref for the pnp transistor current sources). This arrangement comprises a first branch using the collector-emitter paths connected in series of two transistors: pnp transistor T₁₀ and npn transistor T₄₁. The emitter-base path of a pnp transistor T'₄₀ whose collector is connected to ground being inserted between the base and the collector of the transistor T₄₀. A resistor R₄₀ is inserted between the emitter(s) of the transistor T₄₁ and ground. The second branch comprises in a series connection the emitter-collector paths of a pnp transistor T₄₁ and an npn transistor T₄₃ whose emitters are connected to ground. The base-emitter path of an npn transistor T'₄₃ is connected between the collector and the base of the transistor T₄₃. The emitters of the transistors T₄₀ and T₄₁, are brought to a value which is equal to three diode voltages (3 V_(D)). This voltage which is equal to 3 V_(D) is obtained on the basis of the voltage V which feeds a current source I_(o) which causes a current I_(o) to flow through three series-arranged diodes D₄₀, D₄₁ and D₄₂. The voltage Vref is available on the interconnected bases of the transistors T₄₀ and T₄₁, and a voltage V'ref on the interconnected bases of the transistors T₄₁ and T₄₃. These values specifically depend on the value of resistor R₄₀.

The circuit according to the invention (FIG. 3) is distinguished from that shown in FIG. 1 in that transistor T₁₂ and npn transistor T₁₄ and diodes D₁₀, D₁₂ and D'₁₂ are inserted. The transistor T₁₂ has its base connected to the reference voltage source Vref, its emitter connected to the supply voltage source V and it has one or various collectors connected to ground through two forward direction diodes D₁₂ and D'₁₂. The transistor T₁₂ constitutes a current source zI_(o), the emitter of the transistor T₁₄ is connected to ground and its collector is connected to that or those of the transistor T₁₂.

A diode D₁₀ is inserted between the collectors of the transistors T₁ and T₁₄, whilst its anode is connected to the collector of the transistor T₁. So four operating zones are distinguished:

(a) Low I_(L) : k_(o) I_(L) <xI_(o)

The transistor T₀ is saturated, the transistor T₁ is blocked as is the transistor T₁₄. The current zI_(o) passes through the diodes D₁₂ and D'₁₂ and the value of the collector potential of T₁₂ is 2V_(D).

The transistor T₂ is conductive. Its collector potential value is the sum of the base-emitter voltages of the transistors T₂ and T'₂, that is, 2V_(D), which implies that the diode D₁₀ is blocked. The operation is thus the same as above and we have:

    I=I.sub.o (1+y), which corresponds with a maximum gain.

(b) Lower intermediate I_(L) : k_(o) I_(L) >xI_(o).

The transistor T₁₀ is passed through by the current K_(o) I_(L) -xI_(o).

The transistor T₁₄ which has w emitters (in the drawing w=3) is passed through by the current w(k_(o) I_(L) -xI_(o)).

The diodes D₁₂ and D'₁₂ are passed through by the current zI_(o) -w(k_(o) I_(L) -xI_(o)), thus the voltage across the collector of T₁₄ has the value 2V_(D). The transistor T₂ is conductive, thus the voltage on the base of T'₂ and thus on the collector of T₁ has also the value 2V_(D). Thus the diode D₁₀ is blocked.

So this is the same case as with item b) of FIG. 1 that is to say, that the transistor T₂ conducts the current yi_(o) -(k_(o) I_(L) -xI_(o)) as does the transistor T₃.

    Thus we have I=I.sub.o (1+y)-(k.sub.o I.sub.L -xI.sub.o).

    The slope is equal to a-k.sub.o.

(c) Higher intermediate I_(L) : w (kI_(L) -3xI_(o))-zI_(o) >0.

The transistor T₁ conducts the current k_(o) I_(L) -xI_(o), and T₁₄ conducts the current w(k_(o) I_(L) -xI_(o)), but seeing that this current is larger than zI_(o), the transistor T₁₄ tends to be saturated that is, its collector voltage tends towards V_(CE) =0. Once its collector voltage attains the potential V_(D), the diode D₁₀ can be conductive.

The result of this is that the transistors T₁ and T₁₄ each consume current supplied by the source yI_(o).

The transistor T₂ thus conducts the current:

    yI.sub.o -(k.sub.o I.sub.L -xI.sub.o)[w(k.sub.o I.sub.L -xI.sub.o)-zI.sub.o ].

So we have:

    I=I.sub.o (1+y)-((w+1)k.sub.o I.sub.L +(w+1)xI.sub.o +zI.sub.o.

The slope, equal to -(w+1)k_(o) is larger than for item b).

(d) High I_(L) : w(k_(o) I_(L) -xI_(o))-zI_(o) +k_(o) I_(L) -xI_(o) ≧yI_(o)

The transistors T₁ and T₁₄ completely consume the current yI_(o).

The result is that the transistor T₂ is blocked.

So we have I=I_(o).

According to FIG. 4 the two-slope curve of the circuit as depicted in FIG. 3 shows a first part I and a steeper second part II which enables the parts to follow more accurately a characteristic correction-curve running as indicated by way of a solid line in FIG. 5. The presence of this correction curve with two slopes permits to obtain a maximum difference between the theoretical and real curves which is much smaller than with a correction curve having a single slope.

Fractionary ratios x, y and z can be obtained with the reference voltage Vref when using to this effect a circuit of the dividing current mirror type similar to the one described with FIG. 2 for obtaining the current k_(o) I_(L) (transistors T₃₀, T₃₁, diode D₃, resistor R'), or more simply, by varying the surface of the emitters. In fact the numbers of the emitters have been mentioned for clarity. Evidently, the currents have the same ratios as the effective emitter surfaces.

The schematic diagram of FIG. 6 comprises the same elements as that of FIG. 3 arranged in the same fashion but for the fact that the anode of the diode D₁₀ is connected to the collector of the transistor T₁₀ instead of being connected to that of the transistor T₁. As observed hereinbefore, four operating zones are obtained

(a) Low I_(L) : k_(o) I_(L) <xI_(o)

The transistor T_(o) is saturated. The transistor T₁ is blocked, as is transistor T₁₄. The current zI_(o) passes completely through the diodes D₁₂ and D'₁₂. The diode D₁₀ is thus reversely biased.

We have

I=I_(o) (1+y)

(b) Lower intermediate I_(L) : k_(o) I_(L) >xI_(o) and wI₁ <zI_(o)

As the current wI₁ passing through T₁₄, with w=3 in the drawing (because T₁₄ has three emitters), is smaller than zI_(o), the diodes D₁₂ and D'₁₂ are passed by a current which is sufficient for causing a polarization of the conductive diode. The cathode of D₁₀ is thus at a potential of 2V_(BE). The current passing through the transistor T₁₀, and thus the transistor T₁, is not zero. The collector potential of T₁₀ and thus the anode potential of D₁₀ is 2V_(BE). The diode D₁₀ does not pass any current.

We have

    I.sub.1 =k.sub.o I.sub.L -xI.sub.o

    αI.sub.1 =α(k.sub.o I.sub.L -xI.sub.o)

    I=I.sub.o +yI.sub.o -α(k.sub.o I.sub.L -xI.sub.o)

The current I decreases as a function of the line current with a slope -αk_(o) I_(L) (zone I' of FIG. 7).

(c) Higher intermediate I_(L) : k_(o) I_(L) >xI_(o) and wI₁ <zI_(o)

The diodes D₁₂ and D'₁₂ no longer receive current and the voltage of the cathode of D₁₀ begins to drop, thus causing the diode D₁₀ to be conductive. The subtracted current k_(o) I_(L) thus becomes:

    xI.sub.o +(wI.sub.1 -zI.sub.o)+I.sub.1

We have:

    I=I.sub.o +yI.sub.o -αI.sub.1

with

    k.sub.o I.sub.L -αI.sub.o =I.sub.1 +(IwI.sub.1 -zI.sub.o)

from which: ##EQU3##

The current I decreases with a slope which is smaller than in the preceding case b) due to the current subtracted by the diode D₁₀.

This slope has a value of ##EQU4##

(d) High I_(L) : αI₁ >yI_(o)

Transistor T₂ is blocked as is transistor T₃.

We have

    I=I.sub.0.

FIG. 8 shows in what way a gain curve which corresponds with the case of a subscriber telephone set specifically suitable for exchanges having very remote subscribers can be approached.

The schematic diagram of FIG. 9 produces a compensation curve, shown in FIGS. 10 and 11, having three successive slopes enabling a more refined compensation than in the preceding case. From the point of view of the schematic diagram it corresponds with the embodiment of FIG. 6, plus a parallel arrangement of a novel sub-set D₂₀, D₂₂, D'₂₂, T'₁₄. The anode of the diode D₂₀ is connected to the collector of the transistor T₁₀ and the cathode of the diode D₂₀ is connected to the collector-emitter path of the transistor T'₁₄ whose emitter is connected to ground and also connected to series-connected forward direction diodes D'₂₂ and D₂₂, the cathode of D'₂₂ being connected to ground. The base of the transistor T'₁₄ is connected to those of the transistors T₁ and T₁₄.

A transistor T'₁₂ inserted at the current source supplies a current z'I_(o) at the node of the collector T'₁₄, at the cathode of D₂₀ and at the anode of D₂₂. Thus with the aid of these two parallel arrangements we have a curve showing three successive slopes with decreasing values ##EQU5## The transistor T₁₀ shows by way of hypothesis a single emitter, w and w' referring to the number of emitters of the respective transistors T₁₄ and T'₁₄ (or rather the ratio of the emitter surface of this transistor to that of the transistor T₁₀). The choice of w, w', z and z' determines the slopes and the positions of the connecting points. The two sub-sets (D₁₀, D₁₂, D'₁₂ and T₁₄) (D₂₀, D₂₂, D'₂₂, T'₁₄) are driven consecutively and their effects added up in accordance with the same opening principle as used in the previous examples. 

We claim:
 1. Equalizing circuit for producing an output current as a function of the value of an input current in accordance with an output current characteristic having a maximum and a minimum value, which circuit comprises a means for producing a first current which is proportional to the input current, connected in series with a first current source producing a second current which is proportional to a reference current, in order to produce a first resulting current which is positive when the first current is higher than the second current and zero in the opposite case, a first switching stage arranged for being non-conductive when the first resulting current is zero, and passed through thereby when it is positive, a second switching stage arranged for being passed through by the same current as the first switching stage, a second current source arranged for supplying a third current which is proportional to the reference current and connected in series with the second switching stage, in a manner such as to generate a second resulting current which is positive when the third current is higher than the resulting first current, a third switching stage arranged for not conducting when the second resulting current is zero, and for being passed through thereby when it is positive, a first current output stage arranged for supplying a current which is equal to the current passing through the third switching stage and a second current output stage connected in parallel with the first current output stage arranged for supplying a current which is equal to the reference current, whose value is thus the said minimum value of the output current characteristic, characterized in that it comprises at least an equalizing means connected in parallel with one of the first and second switching circuits and comprising on the one hand a third current source (T₁₂) arranged for supplying a fourth current (ZI₀) which is proportional to the reference current, connected in series with a fourth current source (T₁₄) arranged for supplying a current in proportion to the current supplied by the first switching stage and on the other a blocking circuit arranged for connecting the fourth current source in parallel with at least one of the first and second switching circuits when the current passing through the fourth current source is larger than the fourth current.
 2. A circuit as claimed in claim 1, characterized in that the first switching stage comprises a first transistor (T₁₀) whose collector-emitter path is connected in parallel with the first current source and a second transistor (T'₁₀) whose base-emitter path is connected in parallel with the collector-base path of the first transistor (T₁₀) and in that the second switching stage comprises a third transistor (T₁) whose base is connected to that of the first transistor (T₁₀).
 3. A circuit as claimed in claim 2, characterized in that the third switching stage comprises a fourth transistor (T₂) whose collector-emitter path is connected in parallel with the second switching stage and a fifth transistor (T'₂) whose base-emitter path is connected in parallel with the collector-base path of the fourth transistor (T₂) and in that the first output stage comprises a sixth transistor (T₃) whose base is connected to that of the fourth transistor (T₃).
 4. A circuit as claimed in claim 3, characterized in that said blocking circuit comprises a first diode connected in series with the said means for producing the first current which is proportional to the input current, and second an third diodes connected in parallel with the fourth current source (T₁₄).
 5. A circuit as claimed in claim 4, characterized in that said blocking circuit comprises a fourth diode connected in series with the second current source and fifth and sixth diodes connected in parallel with the fourth current source.
 6. A circuit as claimed in claim 3, characterized in that it comprises two equalizing circuits connected in parallel with the first switching circuit.
 7. A circuit as claimed in claim 2, characterized in that said blocking circuit comprises a first diode connected in series with the said means for producing the first current which is proportional to the input current, and second and third diodes connected in parallel with the fourth current source (T₁₄).
 8. A circuit as claimed in claim 7, characterized in that it comprises two equalizing circuits connected in parallel with the first switching circuit.
 9. A circuit as claimed in claim 2, characterized in that said blocking circuit comprises a first diode connected in series with the second current source and second and third diodes connected in parallel with the fourth current source.
 10. A circuit as claimed in claim 1, characterized in that the third switching stage comprises a first transistor (T₂) whose collector-emitter path is connected in parallel with the second switching stage and a second transistor (T'₂) whose base-emitter path is connected in parallel with the collector-base path of the first transistor (T₂) and in that the first output stage comprises a third transistor (T₃) whose base is connected to that of the first transistor (T₂).
 11. A circuit as claimed in claim 1, characterized in that said blocking circuit comprises a first diode connected in series with the said means for producing the first current which is proportional to the input current, and second and third diodes connected in parallel with the fourth current source (T₁₄).
 12. A circuit as claimed in claim 11, characterized in that it comprises two equalizing circuits connected in parallel with the first switching circuit.
 13. A circuit as claimed in claim 1, characterized in that said blocking circuit comprises a first diode connected in series with the second current source and second and third diodes connected in parallel with the fourth current soruce. 